Rate-of-turn sensor

ABSTRACT

For driving and simultaneously evaluating a deflection and/or a rate of motion of an electrostatically excited oscillator element, excitation currents flowing during electrostatic excitation are determined, and deflection and/or the rate of motion of the oscillator element are determined based on the determined excitation currents.

TECHNICAL AREA

The present invention relates to a method for driving and simultaneously evaluating the deflection (x(t)) and/or the rate of motion (v(t)) of an electrostatically excited oscillator element, according to the preamble of claim 1, a circuit design for carrying out the method, according to the preamble of claim 8, and a rate-of-turn sensor according to the preamble of claim 10.

RELATED ART

Micromechanical rate-of-turn sensors are used currently, e.g., in motor vehicles as sensors for driving assistance systems, such as the electronic stability program, ESP, or for roll-tendency compensation. They use the Coriolis effect to measure, e.g., the rate-of-turn of the vehicle around its vertical axis (yaw) or its longitudinal axis (roll).

Micromechanical rate-of-turn sensors contain one or more oscillator elements, which are made to oscillate periodically using electrostatic forces. Each of the oscillator elements includes a mass m located within a plane such that it is capable of oscillating around a rest position. It is also known to excite the oscillator elements, e.g., electrodynamically or piezoelectrically, instead of electrostatically.

Only one oscillating mass will be considered below, for simplicity. Micromechanical rate-of-turn sensors include four capacitor groups (depicted schematically in FIG. 1) composed of one or more capacitors used to excite the oscillator element and measure the oscillating motion. Mechanical springs and dampening elements are not shown in FIG. 1, for simplicity. The plane in which the flat oscillator element lies is the x-y plane. Since the electrostatic forces in capacitors always only ever function in an attracting manner, two capacitor groups C₁ and C₂ are required on either side of the oscillator element for the drive. Capacitor group C₁ generates forces F₁ in the positive x direction, and capacitor group C₂ generates competing forces F₂ in the negative x direction. The separate capacitor groups C₃ and C₄ are used to measure the deflection x(t) and/or rate of motion v(t) of the oscillator element, by way of which the frequency of oscillation and the amplitude of oscillation can be adjusted, using suitable measures, to the mechanical resonant frequency of the oscillating motion or to a fixed, predefined amplitude. Capacitor groups C₃ and C₄ are typically used in a differential measurement, e.g., in order to eliminate parasitic capacitances.

If mass m, which is oscillating in the x direction, is rotated around the z axis, the mass undergoes an additional periodic acceleration in the y direction, which is proportional to the rate of turn. Special measuring devices are required to measure this acceleration, e.g., a second mass m, which is elastically coupled to mass m and which can oscillate in the y direction, and, e.g., two additional precision capacitor groups for measuring the amplitude of oscillation in the y direction. Rate-of-turn sensors with measuring devices of this type are known, e.g., from DE 102 37 410 A1 and DE 102 37 411 A1. The detection of deflections or forces in the y direction is not the subject of the present patent application.

According to the related art, four capacitor groups C₁, C₂, C₃ and C₄ are required to electrostatically excite and measure the deflection x(t) and/or rate of motion v(t) of the oscillator element; this requires high manufacturing expenditure and large dimensions for current rate-of-turn sensors.

DISCLOSURE OF THE INVENTION AND ITS ADVANTAGES

The disadvantages of the related art are avoided with an inventive method of the species described initially by determining the deflection and/or rate of motion of the oscillator element based on the excitation current flowing during electrostatic excitation.

The main point of the present invention is the generation of drive forces F₁ and F₂ and the simultaneous measurement of deflection x(t) and/or oscillator velocity v(t) using only two capacitor groups C₁ and C₂.

The present invention is based on a particular configuration of the excitation voltages U₁(t) and U₂(t) present at capacitor groups C₁ and C₂; the sum of currents i₁(t) and i₂(t) flowing into capacitor groups C₁ and C₂ is evaluated simultaneously.

Compared with the related art, the present invention makes it possible to eliminate capacitor groups C₃ and C₄, thereby enabling, e.g., the sensor to be reduced in size. When the chip surfaces on the sensor made available by eliminating C₃ and C₄ are filled with capacitor groups C₁ and C₂, the level of excitation voltage required can be reduced for the same chip surface area. It is therefore possible, e.g., to eliminate charge pumps to increase the excitation voltage above the available operating voltage.

A BRIEF DESCRIPTION OF THE DRAWING, WHICH INCLUDES

FIG. 1 a schematic depiction of the design of a micromechanical rate-of-turn sensor according to the related art, and

FIG. 2 an inventive circuit design for simultaneously driving a rate-of-turn sensor and measuring its velocity.

WAYS TO IMPLEMENT THE PRESENT INVENTION

Two capacitor groups C₁ and C₂ located in the plane of the oscillating motion, on either side of the oscillator element, are used to excite an oscillator element that is excitable to perform an oscillating motion. Each capacitor group C₁ and C₂ is composed of at least one capacitor. The term “capacitor” refers to any type of capacitive element with which voltage is applied to produce an electrostatic force between the charge carriers that form capacitance, and with which a change in the distance between the charge carriers relative to each other brings about a change in the capacitance.

The two capacitor groups C₁ and C₂, which serve to drive oscillator element, are acted upon with excitation voltages U₁(t) and U₂(t). These two excitation voltages each have a direct component U₀, which is superimposed with a cosinusoidal alternating voltage U_(a)(t) with different signs: U ₁(t)=U ₀ +U _(a)(t) U ₂(t)=U ₀ −U _(a)(t) U _(a)(t)=Û _(a)·cos(ω·t)

In a capacitor, there is a quadratic relationship between applied voltage and the amount of electrostatic force exerted. The following therefore applies for the resultant force F(t) that acts on mass m of the oscillator element; force F(t) is calculated as the difference between forces F₁(t) and F₂(t) acting in the x direction and in the negative x direction: F(t)=F ₁(t)−F ₂(t)F(t)˜[U ₁ ²(t)−U ₂ ²(t)]=4·U ₀ ·U _(α)(t)

A linear relationship results between U_(a)(t) and force F(t) that is exerted. Since U_(a)(t) is a harmonic oscillation, deflection x(t) undergone by mass m and rate of motion v(t) in the steady state will also represent a harmonic oscillation, defined by x(t)={circumflex over (x)}·cos(ω·t+φ) v(t)=−{circumflex over (x)}·ω·sin(ω·t+φ)

Maximum deflection {circumflex over (x)} and phase φ are dependent on the level of the excitation voltages, the excitation frequency, and the oscillation properties. The following applies for the oscillator resonant frequency: φ=−π/2. In this case, v(t) is in-phase with U_(a)(t).

For capacitances C₁(t) and C₂(t) of capacitor groups C₁ and C₂, the following linear—or linearized—dependence applies: C ₁(t)=C ₀ +k _(c) ·x(t) C ₂(t)=C ₀ −k _(c) ·x(t)

C₀ is the basic capacitance at deflection x=0, and k_(c) is a constant that depends on the capacitor geometry. The following applies for the instantaneous charges on the capacitors: Q ₁(t)=C ₁(t)·U ₁(t) Q ₂(t)=C ₂(t)·U ₂(t)

The instantaneous excitation currents i₁(t) and i₂(t) flowing into both capacitors can therefore be calculated, as follows:

${i_{1}(t)} = {\frac{\mathbb{d}Q_{1}}{\mathbb{d}t} = {{{C_{1}(t)} \cdot \frac{\mathbb{d}{U_{1}(t)}}{\mathbb{d}t}} + {{U_{1}(t)} \cdot \frac{\mathbb{d}{C_{1}(t)}}{\mathbb{d}t}}}}$ ${i_{2}(t)} = {\frac{\mathbb{d}Q_{2}}{\mathbb{d}t} = {{{C_{2}(t)} \cdot \frac{\mathbb{d}{U_{2}(t)}}{\mathbb{d}t}} + {{U_{2}(t)} \cdot \frac{\mathbb{d}{C_{2}(t)}}{\mathbb{d}t}}}}$

When the sum of the two excitation currents i₁(t) and i₂(t) is calculated and inserted into the two functions above, the following relationship is observed:

$\frac{{i_{1}(t)} + {i_{2}(t)}}{2 \cdot k_{c} \cdot {\hat{U}}_{a}} = {{- \varpi} \cdot \hat{x} \cdot {\sin\left( {{2 \cdot \varpi \cdot t} + \varphi} \right)}}$

When the sum of the two excitation currents i₁(t) and i₂(t) is compared with rate of motion v(t) of the oscillator element v(t)=− ω·{circumflex over (x)}·sin( ω·t+φ), one sees that the sum of the two excitation currents i₁(t) and i₂(t) have the same parameters amplitude and phase—except for constant coefficient factors—as does rate of motion v(t) of the oscillator element, but with twice the frequency.

FIG. 2 shows the circuit design used to determine the required parameters amplitude and phase of excitation currents i₁(t) and i₂(t). A signal generator 10 delivers signal U_(a)(t), with U _(α)(t)=Û _(α)·cos(ω·t).

A direct-voltage source 20—which is preferably capable of being regulated—delivers signal U₀. Via addition and subtraction steps, the excitation voltages U ₁(t)=U ₀ +U _(α)(t) and U ₂(t)=U ₀ −U _(α)(t) are calculated, then they are sent to the non-inverting inputs of two operational amplifiers 31, 32. Operational amplifiers 31, 32 are each fed back via a resistor R. The inverting inputs of operational amplifiers 31, 32 are connected with capacitor groups C₁ and C₂ of a rate-of-turn sensor 40. One or more oscillator elements are located in rate-of-turn sensor 40, which can be made to oscillate electrostatically via the voltages present at capacitor groups C₁ and C₂. Excitation voltages U₁(t) and U₂(t) for driving the oscillator elements of rate-of-turn sensor 40 are thereby supplied to capacitor groups C₁ and C₂. The output voltages of the two operational amplifiers 31, 32 are calculated as U₀+R·i₁(t) and U₀+R·i₂(t), by way of which excitation currents i₁(t) and i₂(t) are determined. The sum of these two output voltages, which contain the excitation currents, is calculated, and the offset 2·U₀ is subtracted. The resultant signal is used to determine the phase and magnitude in a manner known per se, using a phase and magnitude measuring device 50. To this end, cosinusoidal and sinusoidal reference signals cos(2·ω·t) and sin(2·ω·t) with twice the excitation frequency, which are also generated by signal generator 10, are also sent to phase and magnitude measuring device 50.

Based on the magnitude that was measured, the amplitude of oscillation corresponding to the maximum deflection can now be determined, e.g., in order to regulate it to a certain value by changing U₀ or Û_(a). Based on the phase that is measured, a controlled variable can be determined, with the aid of which the drive frequency can always be is held at the mechanical resonant frequency. At resonance, the required phase is exactly −π/2.

INDUSTRIAL APPLICABILITY

The present invention has industrial applicability, in particular, in the manufacture of micromechanical rate-of-turn sensors, e.g., for use in conjunction with driving assistance systems, such as ESP, roll-tendency compensation, navigation devices, or the like. 

1. A method for driving and simultaneously evaluating a deflection (x(t)) and/or a rate of motion (v(t)) of an electrostatically excited oscillator element, comprising the steps of determining excitation currents (i₁(t), i₂(t)) flowing during electrostatic excitation; and determining the deflection (x(t)) and/or the rate of motion (v(t)) of the oscillator element based on the determined excitation currents (i₁(t), i₂(t)).
 2. A method as defined in claim 1, wherein the electrostatic excitation takes place using capacitor groups (C₁, C₂) located on both sides on the oscillator element in a plane of an oscillating motion, and excitation voltages (U₁(t), U₂(t)) present at the capacitor groups (C₁, C₂) are configured in a particular manner.
 3. A method as defined in claim 2, wherein the excitation voltages (U₁(t), U₂(t)) present at the capacitor groups (C₁, C₂) each have a direct component (U₀), which is superimposed with a cosinusoidal alternating voltage (U_(a)(t)) with different signs for the capacitor groups (C₁, C₂).
 4. A method as defined in claim 2, wherein a sum (i₁(t)+i₂(t)) of the excitation currents (i₁(t), i₂(t)) flowing into the capacitor groups (C₁, C₂) is evaluated in order to determine the deflection (x(t)) and/or the rate of motion (v(t)).
 5. A method as defined in claim 4, wherein the deflection and/or rate of motion of the oscillator element is calculated based on a change in capacitance (C₁(t), C₂(t)) of the capacitor groups (C₁, C₂), which is determined based on the sum (i₁(t)+i₂(t)) of the excitation currents (i₁(t), i₂(t)).
 6. A method as defined in claim 1, wherein the oscillator element is stimulated to make an oscillating motion in a resonant frequency.
 7. A method as defined in claim 1, wherein the rate of motion v(t) is calculated directly from a sum of the excitation currents (i₁(t), i₂(t)), whereby the following applies: $\frac{{i_{1}(t)} + {i_{2}(t)}}{2 \cdot k_{c} \cdot {\hat{U}}_{a}} = {{- \varpi} \cdot \hat{x} \cdot {\sin\left( {{2 \cdot \varpi \cdot t} + \varphi} \right)}}$ and v(t) = −ϖ ⋅ x̂ ⋅ sin (ϖ ⋅ t + φ), where k_(c) is a constant that depends on a capacitor geometry, Û_(a) is a maximum direct component of each of the excitation voltages, {circumflex over (x)} is a maximum deflection, and Φ is a phase, and where the sum of the excitation currents has twice the frequency as compared with the rate of motion of the oscillator element.
 8. A circuit design for carrying out the method as recited in claim 1, comprising a rate-of-turn sensor (40) with at least one oscillator element that is stimulatable to perform an oscillating motion; and means (C₁, C₂) for electrostatically exciting the oscillator element; means (31, 32, 50) for measuring excitation currents (i₁(t), i₂(t)) flowing during electrostatic excitation of the oscillator element; means for calculating a sum (i₁(t), i₂(t)) of the excitation currents; and means (50) for calculating a rate of motion (v(t) of the oscillator element based on the sum (i₁(t)+i₂(t)) of the excitation currents (i₁(t), i₂(t)).
 9. The circuit design as recited in claim 8, further comprising means for calculating a capacitive change in the means (C₁, C₂) for electrostatically exciting the oscillator element based on the measured excitation currents (i₁(t), i₂(t)) and excitation voltages (U₁(t), U₂(t)); and means for calculating a deflection of the oscillator element based on the change in capacitance. 